With the growing interest in time-interleaved (TI) structures, the conversion rates of ADCs have greatly improved, which has inevitably increased power consumption. Despite the advantages of TI structures, power consumption is increased due to the stricter matching requirements between channels; in some cases, >50% of total power is for calibration purposes [1]. Thus, to realize high-speed and high-resolution ADCs with TI structures, it is important to alleviate the calibration burden by choosing a suitable number of power-efficient high-speed single channels. Previously reported CDAC-based 2b/cycle structures [2][3][4][5] made contributions in realizing high-speed single-channel ADCs [2-4] with high resolution [5] by using additional capacitive DACs and modified switching logic. The power overhead and the complexity of the additional logic and DACs for 2b/cycle implementations have been of trivial concern for low resolution ADCs. However, as resolution increases, the complexity of such circuits becomes considerable, with power taking up a big share of the total. In this paper, a multi-step hardware-retirement (MSHR) technique, which disables low-accuracy hardware blocks of scaled sizes with the requirement relaxations from redundancies in an advancement to the reconfiguration scheme in [5], is reported to alleviate the overhead of additional logic and DACs for ADCs, requiring high resolutions. A low-power 2.6b/cycle-based SAR ADC architecture is presented as a proof of concept. Figure 26.7.1 shows a block diagram of the single-end equivalent 10b SAR ADC with 2.6b/cycle architecture. The SAR ADC includes three DACs (SIG-DAC, REF-DAC1, REF-DAC2) and five comparators (CMP0-4). The sizes of REF-DAC(1,2) are designed to be 1/4 of SIG-DAC, while those of CMP(0,1,3,4) are set to be 1/4 of the CMP2, respectively, thanks to the implementation of the MSHR technique with redundancies. The overall sizes of DACs and comparators are 1.5 and 2 times the sizes of SIG-DAC and CMP2, respectively, making the hardware compact. REF-DAC(1,2) form decision thresholds for code decisions independent of the input. The capacitor switching operations of REF-DAC(1,2) are merged with the reference switches shared between REF-DAC1 and REF-DAC2, as shown in Fig. 26.7.1 to simplify control logic. Unlike the REF-DAC, SIG-DAC samples the input and forms a residue after each bit decision.Note that only one SIG-DAC is employed, making the complexity of input-dependent control logic comparable to that of conventional 1b/cycle architectures. A total of 12 cycles are used for a complete single-channel SAR bit decision, where 4 cycles are allocated for sampling purposes. Within the 4 sampling cycles, only 3 cycles are used for pure sampling, while 1 cycle is used to reset SIG-DAC to alleviate the burden of the input driver and to improve sampling linearity. Figure 26.7.2 shows a schematic of SIG-DAC and a descriptive table of the overall structure. Within the total of 536C in SIG-DAC, a total redundancy of 24C is utilized, making the effective referenc...